A High-Gain Wideband Fabry-Pérot Antenna Employing a Water-Based Frequency Selective Surface for Polarization- and RCS-Reconfigurability

Wang, Ying; Liu, Zhiming; Zhou, Huilin; Bornemann, Jens; Wang, Yuhao; Kong, Xiangkun

doi:https://doi.org/10.1155/2024/1804375

International Journal of RF and Microwave Computer-Aided Engineering

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Abstract Introduction Conclusions Data Availability Conflicts of Interest Acknowledgments References Copyright Related Articles

Research Article | Open Access

Volume 2024 | Article ID 1804375 | https://doi.org/10.1155/2024/1804375

A High-Gain Wideband Fabry-Pérot Antenna Employing a Water-Based Frequency Selective Surface for Polarization- and RCS-Reconfigurability

Ying Wang,¹Zhiming Liu,¹Huilin Zhou,¹Jens Bornemann,²Yuhao Wang,¹and Xiangkun Kong³

Academic Editor: Lu Guo

Received19 Jun 2023

Revised13 Nov 2023

Accepted14 Dec 2023

Published10 Jan 2024

Abstract

A Fabry-Pérot (FP) antenna with wideband dual-polarization and radar cross section- (RCS-) reconfigurability adopting water-based frequency selective surface (FSS) is presented. The feed antenna is designed to switch between horizontal polarization (HP) and vertical polarization (VP) by controlling the on/off states of two PIN diodes. By optimizing the height of the FP resonant cavity, the proposed FP antenna achieves wideband and high-gain properties. In addition, the incident wave can be absorbed when the polymethyl methacrylate (PMMA) container is filled with water, which reduces the monostatic RCS. This design can be selected to be in stealth mode or radiation mode by injecting water into or extracting water from the water container. The measured results indicate that in stealth mode, the 10-dB RCS reduction band is from 4.5 GHz to 6.4 GHz, and the peak RCS reduction is 31.5 dB at 5.2 GHz. In the radiation mode, the realized gains of the FP antenna in both HP and VP at 5.2 GHz reach 16.6 dBi. Simulated and measured results verify the realizability and operational concept of the designed FP antenna.

1. Introduction

Fabry-Pérot (FP) antennas, also known as partially reflecting surface (PRS) antennas, have attracted a high level of attention among antenna researchers due to their simple feeding structure, highly directive radiation pattern, and high-gain performance [1–3]. The array antenna can also be used to effectively improve the gain of the antenna, but the array antenna has obvious shortcomings such as complex feeding network [4]. FP antennas typically consist of a feed antenna, and a PRS. From the ray theory, the FP antenna can achieve significant gain enhancement by making full use of the electromagnetic characteristics of PRS.

Polarization reconfigurable antennas also have a very wide range of application scenarios such as suppressing fading losses and enhancing the capacity of wireless communications [5–7]. In practical applications, many FP antennas with polarization reconfigurable performance have been proposed [8–10]. It is not only possible to realize the FP antenna’s reconfigurability by changing the feed antenna, but also to achieve reconfiguration by controlling the PRS [11, 12]. Also, the direction of polarization of the antenna can be controlled by adding semiconductor devices, such as p-i-n diode and varactor diode [13, 14]. Moreover, FP antennas have good applications in high-frequency bands, including the millimeter-wave band. References [15, 16] demonstrate the successful utilization of 3D printing materials for manufacturing antennas, resulting in impressive radiation performance.

In recent years, there has been an increasing focus among researchers in the field of antenna research on reducing the RCS, alongside endeavors to expand frequency bandwidth and improve realized gain, resulting in some satisfactory progress [17, 18]. The reduction of RCS in antennas plays a crucial role in achieving stealth mode in communication devices, and it also significantly influences the stealth capabilities of defense electronic equipment [19, 20].

Several approaches have been proposed to achieve RCS reduction for FP antennas [21–29]. In [21], two PRSs based on phase gradient metasurface (PGM) were designed to realize wideband RCS reduction including both in- and out-of-band frequency regions. Ref. [22] designed a checkerboard artificial magnetic conductor (AMC) structure to reduce the RCS over a wide band. Ref. [23] makes use of the reflection phase variations between adjacent FSS unit cells on the metasurface to realize RCS reduction. Polarization conversion metasurfaces (PCMs) and checkerboard-arranged metasurfaces (CAMs) can also be used to reduce the RCS [24–26]. However, these methods have the disadvantage that the reduction values of RCSs were not large enough. Besides, using absorption surfaces (ASs) can reduce RCS in a larger range, and RCS reduction values were relatively large [27]. However, low-RCS antennas with ASs absorb the radiation energy, which greatly reduces the gain of the antenna and even leads to the deterioration of the radiation pattern. These designs mentioned above can achieve outstanding RCS reduction, but they are hard to achieve its reconfigurability [21–27].

In order to solve this problem, some researches have proposed designs involving liquid absorbers [28, 29]. Liquid absorbers have the advantages of high adjustability, fluidity, and reconfigurable properties, and they will have broad application prospects. Ref. [30] achieved ultrawideband high absorptivity from 4.63 to 100 GHz using liquid water. Therefore, water-based absorbers can decrease the RCS to a greater extent. In the microwave frequency band, water has a satisfactory dielectric loss, and the permittivity of water is related to temperature [31, 32]. Through the fluidity of water, a water-based FSS can be designed to selectively reflect, transmit, or absorb certain frequencies of electromagnetic waves, allowing for flexible control over the antenna’s response and RCS. Moreover, antennas incorporating water-based FSS can easily realize RCS reconfiguration characteristics. Furthermore, the high loss and ready availability of water make it stand out in achieving antenna RCS reduction compared to liquid ethanol and liquid metals which are commonly used in liquid absorbers.

In this work, a water-based FSS unit is designed to form a PRS layer of a FP antenna. The designed FP antenna exhibits favorable performance characteristics, including wideband, high gain, polarization-reconfiguration, and RCS-reconfiguration. Through measurements, the FP antenna can reach a maximum realized gain of 16.6 dBi in both the HP and VP. Meanwhile, it achieves a measured 10 dB impedance matching bandwidth () from 4.71 GHz to 5.53 GHz. Also, the 10 dB RCS reduction band of the FP antenna in stealth mode is from 4.5 GHz to 6.5 GHz (36.4%), which is located within the C-band (4-8 GHz), and some radar and satellite communication designs have been applied in this operating frequency band [33–35]. The experimental results demonstrate that the antenna exhibits noteworthy performance metrics. This paper serves as an extension and continuation of our previously published work [36].

2. Water-Based FSS and Feed Antenna

2.1. Water-Based FSS Unit

The water-based FSS unit is a three-layer structure that can be decomposed into a polymethyl methacrylate (PMMA) container, a water layer, and a bottom F₄BM265 substrate (, ) with an etched square metal patch. The designed water-based FSS unit is shown in Figure 1(a). The container is located on the top layer and made of PMMA material (, ), forming a closed water storage structure with the bottom substrate. There is a groove in the middle of the container. The side length of the square at the bottom of the groove is , and the height is . The groove is used as the water layer. Figure 1(b) shows the hierarchical structure of the unit. The edge-to-edge distance of the bottom square metal patch from the substrate is 0.4 mm.

(a)

(b)

The water-based FSS unit serves as an absorber. The influence of different parameters on the absorption band is shown in Figures 2(a) and 2(b). In Figure 2(a), it is observed that has an effect on the absorption band, but the changes caused by this effect are acceptable. As shown in Figure 2(b), as decreases, the absorption band becomes narrower, and the value of also decreases. However, the overall absorption band of the absorber shifts towards higher frequencies. The reason for the change of the absorption band is that different parameters will affect the impedance match between the absorber and free space.

(a)

(b)

To achieve the optimal properties of the absorber, the final parameters are obtained as mm, mm, mm, and mm. Figure 3(a) shows the simulated model of the water-based FSS unit. As shown in Figure 3(b), comparing of the FSS unit with and without water, it can be found that decreases significantly after water injection. The absorption band () is from 3.8 GHz to 6.5 GHz. From Figure 3(c), it can be observed that the absorptivity of the FSS unit exceeds 90% in the range of 4.77 GHz to 6.45 GHz, with a maximum value of approximately 98.5% at 5.5 GHz.

(a)

(b)

(c)

2.2. Feed Antenna

Figure 4 shows the schematic diagram of the slot-coupled patch antenna (i.e., feed antenna). The required parameters are summarized in Table 1. The linear polarizations in two orthogonal directions are realized by two perpendicularly positioned H-shaped slots etched on the ground plane. The feed lines are printed on the bottom of substrate 1. And the polarization direction of the antenna is controlled by two PIN diodes labeled as PIN 1 and PIN 2. The two PIN diodes are soldered into the feedlines. If PIN 1 is forward biased and PIN 2 is reverse biased, the antenna radiates vertical polarized waves. Similarly, if PIN 2 is forward biased and PIN 1 is reverse biased, the antenna radiates horizontal polarized waves. Also, in order to further widen the antenna’s operating bandwidth, a square metal patch is printed on the top of substrate 2. Both layers of dielectric substrate are F₄BM265 material.

Figures 5(a) and 5(b) show the simulated and realized gain of the dual-polarized feed antenna. For this case, the feed antenna has a common 10 dB return loss bandwidth of 5-5.7 GHz and a maximum realized gain of 8.7 dBi at 5.6 GHz for both HP and VP. In Figure 5(a), it can be found that even though the 10 dB impedance bandwidths are almost the same in both horizontal and vertical polarizations, there are still some deviations in values. This difference is caused by the H-shaped slots etched on the ground plane. This is because there is a modest deviation between the positions of the H-shaped slots corresponding to different polarizations, which affects the distribution of electromagnetic waves. Figure 5(b) shows that the realized gains in two polarizations are nearly the same.

(a)

(b)

3. Reconfigurable FP Antenna

3.1. FP Antenna in Radiation Mode

The characteristics of the FP antenna are closely related to the height of the FP cavity. The resonance equation of the FP antenna is as follows: where is the height of the FP cavity. Additionally, and , respectively, represent the reflection phases of the PRS layer and ground plane. When the reflection properties of PRS and cavity height satisfy Equation (1), the FP resonant mode can be excited to achieve gain enhancement.

FP antenna consists of a feed antenna and a PRS layer. In this design, the PRS layer adopts the water-based FSS unit mentioned in Section 2. The antenna uses FSS units to form the PRS layer. Figure 6 shows the working schematic diagram of the FP antenna. The spacing between the square metallic patches located at the bottom of the PRS is 0.8 mm. The incident wave can be partially reflected through the metal patch and the gap between them, thus increasing the gain. The height of the cavity has a significant impact on the resonance conditions. Figures 7(a) and 7(b) compare and realized gain at different heights of the cavity. According to Figure 7, when the height of changes, the simulated and realized gain are obviously different. The simulated results verify the above statements.

(a)

(b)

When , the simulated curve moves up significantly, and the 10 dB operating band is greatly reduced. Moreover, although the simulated of the FP antenna has a common 10 dB operating band when mm and mm, the frequency point corresponding to the gain peak can have a larger offset when mm. This is due to the change of cavity resonant frequency caused by the change of cavity height. Considering the comprehensive performance of the FP antenna, the realized gain of the FP antenna reaches 16.9 dBi in HP and 16.7 dBi in VP at 5.2 GHz when mm. Figure 8 compares the realized gain of the feed antenna and FP antenna. It can be observed that the realized gain of the FP antenna increases by more than 5 dB compared to the feed antenna in the frequency range of 4.5 GHz to 5.6 GHz. At 5.2 GHz, the peak gain enhancement within the operating band is increased by 9 dB, which shows a superior high-gain performance of the FP antenna.

3.2. FP Antenna in Stealth Mode

The simulated results of the designed FSS unit show that the FSS unit has considerable absorptivity, which lays a good theoretical foundation for the FP antenna to realize stealth mode. In this design, a method is presented to achieve a reconfigurable RCS by injecting water into and extracting water from the PRS layer. After water injection, the working schematic diagram of RCS reduction is depicted in Figure 9. The incident wave can be absorbed by the PRS layer rather than reflected in other directions when the PMMA container is filled with water.

The simulated monostatic RCS of the proposed FP antenna with and without water injection in the PMMA container are shown in Figure 10. It can be observed that the simulated monostatic RCS of the proposed antenna is reduced by more than 10 dB between 4.5 GHz and 6.5 GHz, with a maximum RCS reduction of 35 dB at 5.2 GHz. Since the temperature can affect the permittivity of water, the RCS reduction curves of the antenna at different temperatures are shown in Figure 11. It can be found that RCS reduction bands of the antenna are similar at 0°C, 25°C, and 50°C, but it would be the best at 25°C. The simulated results show that the proposed antenna can effectively reduce RCS in stealth mode.

(a)

(b)

4. Fabrication and Measurement

To demonstrate the reliability of the above design, the antenna has been fabricated and measured. The PRS layer is mounted over the ground plane with a height of using nylon screws and nuts. As shown in Figure 12, the feed antenna is printed on a 1 mm-thick F₄BM265 (, ) substrate. The measurements of the fabricated antenna were completed in the experimental environment shown in Figure 13. A pair of standard horn antennas and a vector network analyzer are used to complete the measurement in the microwave anechoic chamber.

(a)

(b)

(a)

(b)

(c)

The measured results in Figure 14 show that the feed antenna has 10 dB impedance bandwidths of 4.87-5.69 GHz and 5.00-5.72 GHz, and maximum realized gains of 8.56 dBi and 8.71 dBi, respectively, at 5.6 GHz for HP and VP. Figure 15 shows the and the realized gain of the FP antenna without water for horizontally and vertically polarized waves. According to the results in Figure 15, the FP antenna has a common measured 10 dB impedance bandwidth of 4.71-5.53 GHz, and a maximum gain of 16.6 dBi at 5.2 GHz.

(a)

(b)

(a)

(b)

(c)

(d)

Figure 16 shows the monostatic RCS of the antenna with and without water. Due to machining errors of components and the inability to remove all air bubbles when water is injected into the PMMA container, it is difficult to achieve complete consistency between the measured results and the simulated results. We randomly placed some bubbles of different sizes in the water layer to simulate the possible errors in the measurement. The measured results show that even in the presence of unavoidable external factors such as bubbles, the antenna can still significantly reduce the RCS. Obviously, the measured results are similar to the simulated results, and both of them show superior RCS reduction performance.

Figure 17 shows the measured and simulated co-and cross-polarization radiation patterns of the proposed FP antenna in the E- and H-planes at 4.8 GHz, 5.1 GHz, and 5.4 GHz. The measured results are in good proximity with simulations and illustrate that the antenna has superior radiation characteristics in the operating band.

(a)

(b)

(c)

(d)

(e)

(f)

Table 2 lists some performances of this antenna and other works. It can be seen that this design is a compromise solution. By utilizing the RCS reconfigurable performance of the antenna, it is aimed at balancing the performance in radiation and stealth modes, enabling it to perform well in both modes. It shows that the proposed antenna has excellent 10 dB impedance bandwidth, gain enhancement, and 10 dB RCS reduction band. The measured results are close to the simulated results, reflecting the realizability of the antenna.

5. Conclusions

An RCS-reconfigurable dual-polarization FP antenna using water-based FSS is proposed. Through two PIN diodes, this antenna can switch between horizontal and vertical polarization. The maximum gain enhancement can reach up to 9 dB compared to the feed antenna. Compared with the feed antenna, the realized gain increased by a maximum of 9 dB after adopting the FP resonant cavity. The results show that the designed FP antenna has a common measured 10 dB return loss bandwidth from 4.71 GHz to 5.53 GHz for both HP and VP. The peak realized gain is 16.6 dBi at 5.2 GHz. In addition, the RCS reconfigurability of the proposed antenna can be flexibly achieved by injecting water into and extracting water from the PMMA container. The results show that the monostatic RCS has a maximum reduction of 30.8 dB after water injection. The 10 dB RCS reduction band is from 4.5 GHz to 6.4 GHz which includes the operating frequency band in radiation mode. The simulated and measured results indicate that the proposed antenna exhibits excellent radiation performance and RCS reconfiguration capability.

Data Availability

The data are available on request from the authors.

Conflicts of Interest

The authors declare that they have no conflicts of interest.

Acknowledgments

This work was supported by the National Natural Science Foundation of China (Grant numbers 62201240, 62161027, and 62061030), the Open Fund of the key laboratory of radar imaging and microwave photon technology of the Ministry of Education (Grant number NJ20220005), the Jiangxi Provincial Natural Science Foundation (Grant number 20224BAB212005), and Open research project of the science and technology innovation platform (Huaqiao University) of Fujian Key Laboratory of Special Energy Manufacturing (Grant number FKLSEM-2022-04).

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Copyright © 2024 Ying Wang et al. This is an open access article distributed under the Creative Commons Attribution License, which permits unrestricted use, distribution, and reproduction in any medium, provided the original work is properly cited.

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